Design and test of an RF acceleration system loaded with magnetic alloy for the proton synchrotron of the Xi’an Proton Application Facility

Design and test of an RF acceleration system loaded with magnetic alloy for the proton synchrotron of the Xi’an Proton Application Facility 1 2 3 first-author 1 2 3 corresp Corresponding author, zhengsx@tsinghua.edu.cn Corresponding author, zhengsx@tsinghua.edu.cn zhengsx@tsinghua.edu.cn 1 2 3 4 4 4 1 2 3 1 2 3 1 2 3 1 2 3 Laboratory of Particle & Radiation Imaging, Tsinghua University, Ministry of Education, Beijing 100084, China Laboratory of Particle & Radiation Imaging, Tsinghua University, Ministry of Education, Beijing 100084, China Laboratory for Advanced Radiation Sources and Application, Tsinghua University, Beijing 100084, China Laboratory for Advanced Radiation Sources and Application, Tsinghua University, Beijing 100084, China Department of Engineering Physics, Tsinghua University, Beijing 100084, China Department of Engineering Physics, Tsinghua University, Beijing 100084, China Beijing Institute of Radio Measurement, Beijing 100084, China Beijing Institute of Radio Measurement, Beijing 100084, China The Xi’an Proton Application Facility (XiPAF) is a facility dedicated to the experimental simulation of the space radiation environment. The facility uses a compact synchrotron as its final stage accelerator. The synchrotron can accelerate a proton beam from 7 to 230 MeV. Physical design results show that the radio frequency (RF) acceleration system should work in the frequency range of 1–6 MHz and provide a maximum voltage of >800 V. To dilute the strong space charge effect during the injection period, we also aim to achieve multiharmonic acceleration. A compact RF acceleration system loaded with magnetic alloy cores has been designed and developed to fulfill these requirements. The preliminary test results show that the system can work normally with a gap voltage of 800 V. With a further RF power upgrade, the voltage can be improved to >1.2 kV. Proton synchrotron RF acceleration Magnetic alloy 1 Introduction 1 The Xi’an Proton Application Facility (XiPAF) is a facility dedicated to the experimental simulation of the space radiation environment, especially the investigation of the single event effect (SEE) [ 1 1 ]. The facility uses a compact proton synchrotron [ 2 2 ] as its final-stage accelerator. The synchrotron can accelerate a proton beam from 7 to 230 MeV changeably, which means the radio frequency (RF) system should work in a wide band of ∼1–6 MHz. Although the synchrotron works in slow cycling mode, we aim to achieve a large acceleration voltage of 800 V. With higher acceleration voltage, the synchrotron can provide a larger momentum acceptance. Therefore, we may eliminate the debuncher cavity in the injection line. The maximum beam intensity after injection is ∼ 2×10 11 protons per pulse (ppp). The space charge effect is very significant during the early acceleration stage. Consequently, we plan to introduce the second harmonic wave to reduce the bunching factor, which can suppress the space charge effect. A compact RF acceleration system loaded with magnetic alloy (MA) is proposed to fulfill the requirements of XiPAF’s synchrotron. Compared with ferrite, the traditional loading material, MA has a much higher saturation flux density, a very low Q value, and much better thermal stability [ 3 3 ]. Because of these properties, MA is considered a good option as the load material of the cavity for low- and medium-energy proton synchrotrons. The low-Q-value property allows the system to work in a wide frequency band without active tuning control. This property results in a simple system that is favored in medical ion synchrotrons [ 4 4 - 6 6 4-6 ]. Because of the high saturation flux density and good thermal stability of MA, it can provide a high acceleration gradient, which can significantly shorten the length of the acceleration system. Some rapid cycling synchrotrons [ 7 7 , 8 8 ] and fixed-field alternating gradient accelerators [ 9 9 ] have applied high-gradient cavities loaded with MA. Beam acceleration with multiharmonics can reduce beam loss from the space charge effect in high-intensity machines [ 10 10 , 11 11 ]. The low-Q-value property of MA also makes it possible to apply multiharmonics in the same cavity, thus resulting in a shorter total cavity length[ 12 12 , 13 13 ]. Based on the measured data of the MA core, in this study we design and develop a compact RF acceleration system for XiPAF’s proton synchrotron. We present the main considerations and detailed design of the whole system. Test experiments are conducted to verify the performance of the system under high-power condition. The performance limitation of the system is also revealed through experimental data and thermal analysis. 2 System design 1 2.1 Design targets 2 XiPAF’s synchrotron works in slow cycling mode, with an injection energy of 7 MeV and an extraction energy that varies from 60 to 230 MeV. The ramping time varies from 0.25 to 0.5 s and the maximum ramping speed is 5 T/s. The typical RF voltage and frequency patterns of XiPAF’s synchrotron are shown in Fig. 1 Fig. 1 . The voltage is ramped slowly in 10 ms to the maximum acceleration voltage to capture the beam adiabatically into the longitudinal bucket. The second harmonic RF only operates during the low-energy stage to increase the acceptance of the RF bucket and suppress the space charge effect. After reaching the target beam energy, the fundamental RF voltage is reduced to a low value to suppress the momentum spread and reduce power consumption. The design targets of the RF system of XiPAF’s synchrotron are listed in Table 1 Table 1 [ 14 14 ]. The initial beam energy spread is a major limitation of the acceleration efficiency of low-energy proton synchrotrons working in the slow cycling mode. One solution is to use a debuncher cavity to reduce the injection beam’s energy spread, but this would make the whole system more complicated to build and operate. In the case of XiPAF, multiparticle simulation demonstrates that, with a relative large RF voltage of ∼ 800 V and good system stability, the RF bucket’s momentum acceptance becomes sufficiently large to directly accelerate the injection beam with high efficiency. Compactness is another important requirement for the system, as the free space on the ring left for the RF cavity is ≤1.0 m. For easy operation, we plan to use a low-power-consumption design and forced air to cool the system. 1 1 Parameters 1 1 Values 1 1 Nominal voltage (V) 1 1 800 1 1 Operation frequency (MHz) 1 1 1-6 1 1 Power consumption (kW) 1 1 <1.2 1 1 Voltage stability (%) 1 1 <±2 1 1 Phase stability (°) 1 1 <±0.5 1 1 Length (mm) 1 1 <800 1 1 Outer diameter (mm) 1 1 <600 1 1 Cooling method 1 1 Forced air 2.2 MA cores 2 The shunt impedance R p of the MA core can be expressed as [ 16 16 ] <math display="block" id="M1"><mrow><msub><mi>R</mi><mtext>p</mtext></msub><mo>=</mo><mo stretchy="false">(</mo><msubsup><mi>μ</mi><mrow><msub><mrow/><mtext>p</mtext></msub></mrow><mo>'</mo></msubsup><mi>Q</mi><mi>f</mi><mo stretchy="false">)</mo><mi>t</mi><mi>ln</mi><mrow><mo>(</mo><mrow><mfrac><mrow><msub><mi>r</mi><mtext>o</mtext></msub></mrow><mrow><msub><mi>r</mi><mtext>i</mtext></msub></mrow></mfrac></mrow><mo>)</mo></mrow><mn>,</mn></mrow></math> where r o , r i , and t are the outer radius, inner radius, and thickness of the core, respectively. The product <math id="M2"><mrow><mo stretchy="false">(</mo><msubsup><mi>μ</mi><mi>p</mi><mo>'</mo></msubsup><mi>Q</mi><mi>f</mi><mo stretchy="false">)</mo></mrow></math> is independent of the core size and is used to evaluate the performance of the magnetic material. Q is the Q value of the material, defined as <math id="M3"><mrow><msubsup><mi>μ</mi><mtext>s</mtext><mo>'</mo></msubsup><mo>/</mo><msubsup><mi>μ</mi><mtext>s</mtext><mo>″</mo></msubsup></mrow></math> , and <math id="M4"><mrow><msubsup><mi>μ</mi><mrow><msub><mrow/><mtext>s</mtext></msub></mrow><mo>'</mo></msubsup><mo>−</mo><mi>j</mi><msubsup><mi>μ</mi><mrow><msub><mrow/><mtext>s</mtext></msub></mrow><mo>″</mo></msubsup></mrow></math> is the complex permeability of the material. Here, <math id="M5"><mrow><msubsup><mi>μ</mi><mtext>p</mtext><mo>'</mo></msubsup></mrow></math> is calculated as <math display="block" id="M6"><mrow><msubsup><mi>μ</mi><mrow><msub><mrow/><mtext>p</mtext></msub></mrow><mo>'</mo></msubsup><mo>=</mo><msubsup><mi>μ</mi><mtext>s</mtext><mo>'</mo></msubsup><mrow><mo>(</mo><mrow><mn>1</mn><mo>+</mo><mfrac><mn>1</mn><mrow><msup><mi>Q</mi><mn>2</mn></msup></mrow></mfrac></mrow><mo>)</mo></mrow><mn>.</mn></mrow></math> As a dispersive material, the MA’s material property has a dependence on RF frequency f . The impedance of the MA core can be expressed as a parallel form Z core = ( R p )//( jω L p ), where parallel inductance L p is calculated as [ 16 16 ] <math display="block" id="M7"><mrow><msub><mi>L</mi><mtext>p</mtext></msub><mo>=</mo><mfrac><mrow><mi>t</mi><msubsup><mi>μ</mi><mrow><msub><mrow/><mtext>p</mtext></msub></mrow><mo>'</mo></msubsup></mrow><mrow><mn>2</mn><mi>π</mi></mrow></mfrac><mi>ln</mi><mrow><mo>(</mo><mrow><mfrac><mrow><msub><mi>r</mi><mtext>o</mtext></msub></mrow><mrow><msub><mi>r</mi><mtext>i</mtext></msub></mrow></mfrac></mrow><mo>)</mo></mrow><mn>.</mn></mrow></math> The material of the MA core used in this study is 1K107, produced by AT & M (www.AT & M.com). The thickness of the ribbon is 18 μ m and it is insulated by a 2- μ m SiO 2 electric insulator. The filling ratio of the core is ∼ 75%. Several small sample cores have been made to measure the material’s <math id="M8"><mrow><mo stretchy="false">(</mo><msubsup><mi>μ</mi><mi>p</mi><mo>'</mo></msubsup><mi>Q</mi><mi>f</mi><mo stretchy="false">)</mo></mrow></math> product. Based on the measured result, the r o , r i , and t values of the large-sized core are determined to be 450, 300, and 25 mm, respectively, to make the core’s impedance around 50 Ω at 1 MHz. Two large-sized cores (see Fig. 2 Fig. 2 ) are fabricated to test their properties under high-power condition. Our test experiment shows that the large-sized core can sustain 2 kW instantaneous input power, corresponding to an average power density of 1.4 MW m -3 . The core works normally under a 500-W continuous power input without forced cooling [ 17 17 ]. With this power level, each core should be able to produce a voltage of > 200 V; hence, six cores are sufficient for this project. Six large-sized MA cores with similar <math id="M9"><mrow><mo stretchy="false">(</mo><msubsup><mi>μ</mi><mi>p</mi><mo>'</mo></msubsup><mi>Q</mi><mi>f</mi><mo stretchy="false">)</mo></mrow></math> products and good appearance are selected for the project. The measured <math id="M10"><mrow><mo stretchy="false">(</mo><msubsup><mi>μ</mi><mi>p</mi><mo>'</mo></msubsup><mi>Q</mi><mi>f</mi><mo stretchy="false">)</mo></mrow></math> product and Q value of each core are shown in Fig. 3 Fig. 3 . The difference of <math id="M11"><mrow><mo stretchy="false">(</mo><msubsup><mi>μ</mi><mi>p</mi><mo>'</mo></msubsup><mi>Q</mi><mi>f</mi><mo stretchy="false">)</mo></mrow></math> between each core is controlled to < ±10% in the frequency range of 1–6 MHz. The shunt impedances of the cores range from 50 to 120 Ω. 2.3 Cavity structure and impedance 2 The cavity has one acceleration gap and each side of the gap has a quarter-wave resonator, each loaded with 3 MA cores. The mechanical structure of the cavity is shown in Fig. 4 Fig. 4 . As can be seen, three axial fans are installed at the downside of the cavity for core cooling. The diameter of the fan is 162 mm, and the maximum output wind velocity is 5.5 m/s. A detection circuit is installed at the gap to monitor the acceleration voltage for feedback control. The circuit consists of two bridge resistors with impedances of 40 Ω and 4 kΩ, respectively, and the divided voltage is then converted to a single-ended signal by a balun circuit and then transferred to a low-level-RF (LLRF) system. The system employs a power feeding method called "Multiple Power Feeding," which means that each amplifier with an output impedance of 50 Ω is independently coupled with the MA core. The equivalent circuit of the cavity can be represented as shown in Fig. 5 Fig. 5 [ 15 15 ], where C is the equivalent capacitance of the cavity. Here, C is calculated as <math display="block" id="M13"><mrow><mi>C</mi><mo>=</mo><msub><mi>C</mi><mrow><mtext>gap</mtext></mrow></msub><mo>+</mo><msub><mi>C</mi><mrow><mtext>coax</mtext></mrow></msub><mn>,</mn></mrow></math> where C gap is the capacitance of accelerating gap and C coax is the capacitance of coaxial resonator. Here, C gap and C coax are calculated as <math display="block" id="M14"><mrow><msub><mi>C</mi><mrow><mtext>gap</mtext></mrow></msub><mo>=</mo><mfrac><mrow><mi>ϵ</mi><msub><mi>ϵ</mi><mn>0</mn></msub><msub><mi>S</mi><mrow><mtext>cera</mtext></mrow></msub></mrow><mrow><msub><mi>d</mi><mrow><mtext>cera</mtext></mrow></msub></mrow></mfrac><mn>,</mn></mrow></math> <math display="block" id="M15"><mrow><msub><mi>C</mi><mrow><mtext>coax</mtext></mrow></msub><mo>=</mo><mfrac><mrow><mn>2</mn><mi>π</mi><msub><mi>ϵ</mi><mn>0</mn></msub><msub><mi>l</mi><mrow><mtext>coax</mtext></mrow></msub></mrow><mrow><mi>ln</mi><mo stretchy="false">(</mo><msub><mi>r</mi><mrow><mtext>cav</mtext></mrow></msub><mo>/</mo><msub><mi>r</mi><mrow><mtext>in</mtext></mrow></msub><mo stretchy="false">)</mo></mrow></mfrac><mn>,</mn></mrow></math> where ϵ , S cera , and d cera are the relative dielectric permittivity, cross-sectional area, and length of the ceramic gap, respectively, and l coax , r cav , and r in are the length of the coaxial resonator, the outer radius of the cavity, and the radius of the inner conductor, respectively. The impedance of each loop is obtained as <math display="block" id="M16"><mrow><mi>Z</mi><mo>=</mo><msub><mi>Z</mi><mrow><mtext>core</mtext></mrow></msub><mo>/</mo><mo>/</mo><mrow><mo>(</mo><mrow><mfrac><mn>1</mn><mrow><mi>j</mi><mi>ω</mi><mi>n</mi><mi>C</mi></mrow></mfrac></mrow><mo>)</mo></mrow><mn>,</mn></mrow></math> where n is the total number of MA cores in the cavity. The parameters of the cavity are summarized in Table 2 Table 2 . 1 1 Parameters 1 1 Values 1 1 Nominal voltage (V) 1 1 800 1 1 Operation frequency (MHz) 1 1 1-6 1 1 Length (flange to flange) (mm) 1 1 630 1 1 Outer diameter (mm) 1 1 550 1 1 Inner conductor diameter (mm) 1 1 120 1 1 Acceleration gap length (mm) 1 1 30 1 1 Core number 1 1 6 1 1 Core outer diameter (mm) 1 1 450 1 1 Core inner diameter (mm) 1 1 300 1 1 Core thickness (mm) 1 1 25 1 1 Parallel inductance (per core, 3 MHz) ( μ H) 1 1 ∼ 7.3 1 1 Cavity capacitance (pF) 1 1 ∼ 30 1 1 Cavity shunt impedance (3 MHz) ( Ω ) 1 1 ∼ 440 1 1 Cavity power consumption (3 MHz) (W) 1 1 ∼ 730 The impedance seen by each amplifier is measured by a vector network analyzer. The measured results are compared with the calculated values as shown in Fig. 6 Fig. 6 (where only one loop is shown as an example). The measured result is roughly consistent with the calculated result, which indicates that the real capacitance of the cavity is a little smaller than our estimation. The standing wave ratio is < 2.0 in the working band; hence, the power reflection percentage should be < 9%. 2.4 RF power source 2 The block diagram of the whole system is shown in Fig. 7 Fig. 7 . Six wide-band solid-state amplifiers are used as the RF power source. As described in Sect. 2.1, the MA core’s impedance is designed to be ∼50 Ω, so that we can control the reflection power to an acceptable level without special impedance matching. The maximum output power of each amplifier is ∼300 W. The gain of the amplifier decreases from 31.5 to 29.5 dB in the frequency range of 1–6 MHz. The deviation of gain between each amplifier is < ±0.8 dB. As the gain of each amplifier is only ∼ 30 dB, to reach its maximum power level, we added a 20-dB small amplifier to pre-amplify the LLRF signal of the direct digital synthesizer (DDS). The largest distortion of the sine wave comes from the third- order harmonics, whose level is ∼ -23 dBc in the work frequency band. 2.5 LLRF control system 2 Fig. 8 Fig. 8 shows the block diagram of the LLRF control system. As can be seen, the programmed data of amplitude, frequency, and phase of the RF signal are transferred from the central control system via Ethernet to the local memory of the LLRF control system before the operation of the synchrotron. The programmed data are then processed by a feedback control algorithm and then amplified and transmitted to the RF cavity. The amplitude of the output RF signal obtains feedback according to the measured voltage of the RF cavity. A beam position monitor (BPM) is used to detect the radial beam orbit displacement Δ R , and the system uses this signal for frequency feedback compensation. An fast current transformer (FCT) is used to detect the synchrotron phase of the bunched beam. The system then compares the synchrotron phase to the setting phase of the beam, Δ ϕ , and makes an RF phase compensation. The maximum delay of the Δ ϕ feedback is < 10 μ s, which is much smaller than the period of synchrotron oscillation ( ∼ 1 ms). We use one field-p rogrammable gate array (FPGA) and two DSPs for high-speed digital signal processing. The proportional-integral-derivative (PID) control algorithm and feedback control algorithm are implemented in the FPGA. The digital signal processor (DSP) is used to assist in data processing, downloading, and uploading. Two 16-MB synchronous dynamic random-access memory chips are installed on the board to serve as the local memory of the LLRF control system. 3 High-power-experiment results 1 High-power experiments were conducted to examine the performance of the proposed system. An acceleration voltage of 800 V is achieved in the frequency range of 1–6 MHz. We have also built a wave of dual harmonics in the same cavity to verify the wide-band property of the cavity. The sample voltage waveforms of both single and dual harmonics are shown in Fig. 9 Fig. 9 . Owing to the wide-band property of the cavity, the waveform of the gap voltage suffers from the higher order harmonic of the power source, as shown in Fig. 9 Fig. 9 . The spectrum analysis of the gap voltage waveform shows that the main distortion also comes from the third-order harmonic and its level is < -20 dBc. The input and reflection power of each loop to build an 800-V gap voltage are measured. Because of the spread of the gain factor between each amplifier, the input power of each loop has a spread of ∼ ±40 W. The total input power P in and reflection power P re are shown in Fig. 10 Fig. 10 . The input power is consistent with the calculated result. The theoretical reflection power of each is ≤10 W, which is too small to be measured accurately. Thus, the measured total reflection power is not well consistent with the calculation result. For the MA core used in this project, the maximum magnetic flux density in the core with an input power of 1 kW/core is only 33 mT (at 1 MHz), which is much less than the saturation flux density of the material. Thus, the maximum voltage that the cavity can reach depends on the performance of the cooling system. The balance temperature rise of the core surface can be estimated by using the equation <math display="block" id="M17"><mrow><mi>Δ</mi><mi>T</mi><mo>=</mo><mfrac><mrow><mi>g</mi><mo stretchy="false">(</mo><mi>r</mi><mo stretchy="false">)</mo></mrow><mi>α</mi></mfrac><mfrac><mi>t</mi><mn>2</mn></mfrac><mn>,</mn></mrow></math> where α is the convection coefficient between the core and cooling air, and g ( r ) is the volume energy density at a core radius r . In addition, g ( r ) is inversely proportional to r and can be expressed as <math display="block" id="M18"><mrow><mi>g</mi><mo stretchy="false">(</mo><mi>r</mi><mo stretchy="false">)</mo><mo>=</mo><mfrac><mi>P</mi><mrow><mn>2</mn><mi>π</mi><mi>t</mi><mi>ln</mi><mo stretchy="false">(</mo><msub><mi>r</mi><mi>o</mi></msub><mo>/</mo><msub><mi>r</mi><mi>i</mi></msub><mo stretchy="false">)</mo></mrow></mfrac><mfrac><mn>1</mn><mrow><msup><mi>r</mi><mn>2</mn></msup></mrow></mfrac><mn>,</mn></mrow></math> where P is the RF power consumed by the core. The maximum temperature rise should occur near the inner core radius r i . The convection coefficient α of air-cooling is difficult to estimate. Therefore, we examine the maximum surface temperature of the core with a thermal camera under a constant gap voltage. The experimental results are shown in Fig. 11 Fig. 11 . With the experimental results of balance temperature, we can estimate that α is ∼17 W/(m 2 ·K) without forced cooling and 55 W/(m 2 ·K) with forced cooling. Assume that a temperature rise of 60℃ is sustainable, the cavity can work normally with an average input power of 2.4 kW, which can build a voltage of > 1.2 kV. In fact, because of the high Curie temperature of MA, this temperature rise limit is very conservative. It should be noted that, in this estimation, it is assumed that heat only conducts along the thickness direction of the core and that the core is only cooled by air convection. Consequently, these values can serve as a rough reference for other systems using a similar cooling method. An off-line control experiment was conducted to verify the performance of the LLRF control system. The work pattern was successfully built on the cavity as shown in Fig. 12 Fig. 12 . The voltage envelope is consistent with the setting because the frequency dependence of the system is well compensated by the voltage amplitude feedback loop. The stability of the system is measured as shown in Fig. 13 Fig. 13 . The amplitude ripple level is notably dependent on the amplitude. The amplitude ripple can be controlled to ± 1.0% if the voltage is > 650 V. The phase ripple is well below ± 0.4° for all amplitude cases. 4 Summary 1 A compact RF acceleration system loaded with MA cores is developed for XiPAF’s proton synchrotron. The cold and high-power test experiments show that the performance of the system is well consistent with our design. High-power experiments show that the MA core made of 1K107, which has not been widely used in this area before, could be a good option for similar systems. The acceleration voltage can reach 800 V in the frequency range of 1–6 MHz with an input power of ∼0.8 kW. Furthermore, the thermal analysis shows that, with a further RF power upgrade, the system can work normally with a voltage of >1.2 kV. Owing to the wide-band property of the cavity loaded with the MA core, the waveform of the gap voltage is easily distorted by the low-order harmonic component of the power source. Therefore, the harmonic level of the amplifier should be carefully controlled. Further on-line experiments will be conducted to improve and verify the beam–cavity feedback loop. Finally, although the system is dedicated to XiPAF’s proton synchrotron, its performance should satisfy the requirement of medical proton synchrotrons in slow cycling mode with minor system changes. References S.X. Zheng , Q.Z. Xing , X.L. Guan et al ., Design of the 230 MeV proton accelerator for Xi’an proton application facility , in proceedings of HB 2016 , p. 55 . Design of the 230 MeV proton accelerator for Xi’an proton application facility G.R. Li , X.L. Guan , X.W. 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Cold and high power test of large size magnetic alloy core for XiPAF’s synchrotron The authors are grateful to Prof. Hong Sun, Dr. Xiao Li, and Dr. Hua Shi of IHEP for their enthusiastic help on this project. The authors also appreciate Prof. Zhe Xu for his helpful discussions on the system design. Special thanks should be expressed to Xing Hong of AT&M. Without his professionalism and hard work on the fabrication of MA cores, the project could not have progressed so smoothly. 10.1007/s41365-018-0434-9 2017-05-19 2017-09-15 2017-11-15 2018-05-28 2018-07-01 2021-04-11 © China Science Publishing & Media Ltd. (Science Press), Shanghai Institute of Applied Physics, the Chinese Academy of Sciences, ChineseNuclear Society and Springer Nature Singapore Pte Ltd. 2018 This is a post-peer-review, pre-copyedit version of an article published in Nuclear Science and Techniques. The final authenticated version is available online at: http://dx.doi.org/10.1007/s41365-018-0434-9 http://dx.doi.org/10.1007/s41365-018-0434-9 . 2018 Nuclear Science and Techniques 07 29